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AOZ1016
EZBuckTM 2A Simple Buck Regulator
General Description
The AOZ1016 is a high efficiency, simple to use, 2A buck regulator. The AOZ1016 works from a 4.5V to 16V input voltage range, and provides up to 2A of continuous output current with an output voltage adjustable down to 0.8V. The AOZ1016 comes in an SO-8 package and is rated over a -40C to +85C ambient temperature range.
Features

4.5V to 16V operating input voltage range 130m internal PFET switch for high efficiency: up to 95% Internal Schottky Diode Internal soft start Output voltage adjustable to 0.8V 2A continuous output current Fixed 500kHz PWM operation Cycle-by-cycle current limit Short-circuit protection Under voltage lockout Output over voltage protection Thermal shutdown Small size SO-8 package
Applications

Point of load DC/DC conversion PCIe graphics cards Set top boxes DVD drives and HDD LCD panels Cable modems Telecom/networking/datacom equipment
Typical Application
VIN
C1 22F Ceramic
VIN From PC EN COMP
20k C5 1nF
L1 4.7H
AOZ1016
VOUT LX R2 FB
C4, C6 22F Ceramic R3
C2
AGND
PGND
Figure 1. 3.3V/2A Buck Regulator
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AOZ1016
Ordering Information
Part Number
AOZ1016AI
S nt RoH plia Com
Ambient Temperature Range
-40C to +85C
Package
SO-8
Environmental
RoHS
All AOS Products are offering in packaging with Pb-free plating and compliant to RoHS standards. Please visit wwww.aosmd.com/web/rohs_compliant.jsp for additional information.
Pin Configuration
PGND VIN AGND FB
1 2 3 4 8 7 6 5
LX LX EN COMP
SO-8
(Top View)
Pin Description
Pin Number
1 2 3 4 5 6 7, 8
Pin Name
PGND VIN AGND FB COMP EN LX
Pin Function
Power ground. Electrically needs to be connected to AGND. Supply voltage input. When VIN rises above the UVLO threshold the device starts up. Reference connection for controller section. Also used as thermal connection for controller section. Electrically needs to be connected to PGND. The FB pin is used to determine the output voltage via a resistor divider between the output and GND. External loop compensation pin. The enable pin is active HIGH. Connect EN pin to VIN if not used. Do not leave the EN pin floating. PWM output connection to inductor. Thermal connection for output stage.
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AOZ1016
Block Diagram
VIN
EN
UVLO & POR
5V LDO Regulator
Internal +5V
OTP
+
ISen Reference & Bias
-
Softstart ILimit
Q1
+
0.8V
+
EAmp
- +
FB
-
PWM Comp
PWM Control Logic
Level Shifter + FET Driver
LX
COMP
+ 0.2V -
Frequency Foldback Comparator
500kHz/38kHz Oscillator
0.96V
+ -
Over Voltage Protection Comparator
AGND
PGND
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AOZ1016
Absolute Maximum Ratings
Exceeding the Absolute Maximum ratings may damage the device.
Recommend Operating Ratings
The device is not guaranteed to operate beyond the Maximum Operating Ratings.
Parameter
Supply Voltage (VIN) LX to AGND EN to AGND FB to AGND COMP to AGND PGND to AGND Junction Temperature (TJ) Storage Temperature (TS) ESD Rating(1) 18V
Rating
-0.7V to VIN+0.3V -0.3V to VIN+0.3V -0.3V to 6V -0.3V to 6V -0.3V to +0.3V +150C -65C to +150C 2kV
Parameter
Supply Voltage (VIN) Output Voltage Range Ambient Temperature (TA) Package Thermal Resistance SO-8 (JA)(2)
Rating
4.5V to 16V 0.8V to VIN -40C to +85C 87C/W
Note: 2. The value of JA is measured with the device mounted on 1-in2 FR-4 board with 2oz. Copper, in a still air environment with TA = 25C. The value in any given application depends on the user's specific board design.
Note: 1. Devices are inherently ESD sensitive, handling precautions are required. Human body model rating: 1.5k in series with 100pF.
TA = 25C, VIN = VEN = 12V, VOUT = 3.3V unless otherwise specified(3)
Electrical Characteristics
Symbol
VIN VUVLO IIN IOFF VFB
Parameter
Supply Voltage Input Under-Voltage Lockout Threshold Supply Current (Quiescent) Shutdown Supply Current Feedback Voltage Load Regulation Line Regulation
Conditions
VIN Rising VIN Falling IOUT = 0, VFB = 1.2V, VEN > 1.2V VEN = 0V
Min.
4.5
Typ.
4.00 3.70 2 1
Max.
16
Units
V V
3 10 0.818
mA mA V % %
0.782
0.8 0.5 0.5
IFB VEN VHYS fO DMAX DMIN
Feedback Voltage Input Current EN Input Threshold EN Input Hysteresis Frequency Maximum Duty Cycle Minimum Duty Cycle Error Amplifier Voltage Gain Error Amplifier Transconductance 500 200 2.5 Off threshold On threshold 960 860 150 2.2 VIN = 12V VIN = 5V 97 166 400 100 Off Threshold On Threshold 2.0 160 500
200 0.6
nA V mV
MODULATOR 600 6 kHz % % V/ V A / V 3.6 A mV C ms 130 200
PROTECTION ILIM VPR TJ tSS Current Limit Output Over-Voltage Protection Threshold Over-Temperature Shutdown Limit Soft Start Interval High-Side Switch On-Resistance
OUTPUT STAGE m
Note: 3. Specification in BOLD indicate an ambient temperature range of -40C to +85C. These specifications are guaranteed by design. Rev. 1.1 September 2007
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AOZ1016
Typical Performance Characteristics
Circuit of Figure 1. TA = 25C, VIN = VEN = 12V, VOUT = 3.3V unless otherwise specified.
Light Load (DCM) Operation
Vin ripple
0.1V/div
Full Load (CCM) Operation
Vin ripple
0.1V/div
Vo ripple
20mV/div
Vo ripple
20mV/div
IL 1A/div VLX 10V/div
IL 1A/div VLX 10V/div
1s/div
1s/div
Startup to Full Load
Vin 10V/div
Full Load to Turnoff
Vin 10V/div
Vo 1V/div
Iin 0.5A/div
Vo 1V/div Iin 0.5A/div
400s/div
400s/div
50% to 100% Load Transient
Light Load to Turnoff
Vo Ripple 50mV/div
Vin 5V/div
Vo 1V/div
Io 1A/div
Iin 0.5A/div
100s/div
1s/div
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AOZ1016
Typical Performance Characteristics (Continued) Circuit of Figure 1. TA = 25C, VIN = VEN = 12V, VOUT = 3.3V unless otherwise specified.
Short Circuit Protection Short Circuit Recovery
Vo 2V/div
Vo 2V/div
IL 1A/div
IL 1A/div
100s/div
1ms/div
AOZ1016AI Efficiency
Efficiency (VIN = 12V) vs. Load Current 100 8.0V OUTPUT
95 Efficieny (%)
90
5.0V OUTPUT 3.3V OUTPUT
85
80
75 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 Load Current (A)
Thermal de-rating curves for SO-8 package part under typical input and output condition based on the evaluation board. 25C ambient temperature and natural convection (air speed < 50LFM) unless otherwise specified. Derating Curves at 5V Input
2.5 3.3V, 5.0V OUTPUT Output Current (IO) Output Current (IO) 2.0 1.5 1.0 0.5 0 25 1.8V OUTPUT 2.0 1.5 1.0 0.5 0 25 2.5
8.0V OUTPUT 5.0V OUTPUT 3.3V OUTPUT 1.8V OUTPUT
Derating Curves at 12V Input
35
45
55
65
75
85
35
45
55
65
75
85
Ambient Temperature (TA)
Ambient Temperature (TA)
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AOZ1016
Detailed Description
The AOZ1016 is a current-mode step down regulator with integrated high side PMOS switch and a low side freewheeling Schottky diode. It operates from a 4.5V to 16V input voltage range and supplies up to 2A of load current. The duty cycle can be adjusted from 6% to 100% allowing a wide range of output voltages. Features include enable control, Power-On Reset, input under voltage lockout, fixed internal soft-start and thermal shut down. The AOZ1016 is available in SO-8 package. The AOZ1016 uses a P-Channel MOSFET as the high side switch. It saves the bootstrap capacitor normally seen in a circuit which is using an NMOS switch. It allows 100% turn-on of the upper switch to achieve linear regulation mode of operation. The minimum voltage drop from VIN to VO is the load current times DC resistance of MOSFET plus DC resistance of buck inductor. It can be calculated by equation below:
V O _MAX = V IN - I O x ( R DS ( ON ) + R inductor )
where; VO_MAX is the maximum output voltage, VIN is the input voltage from 4.5V to 16V, IO is the output current from 0A to 2A, RDS(ON) is the on resistance of internal MOSFET, the value is between 97m and 200m depending on input voltage and junction temperature, and Rinductor is the inductor DC resistance.
Enable and Soft Start
The AOZ1016 has internal soft start feature to limit in-rush current and ensure the output voltage ramps up smoothly to regulation voltage. A soft start process begins when the input voltage rises to 4.0V and voltage on EN pin is HIGH. In soft start process, the output voltage is ramped to regulation voltage in typically 2.2ms. The 2.2ms soft start time is set internally. The EN pin of the AOZ1016 is active HIGH. Connect the EN pin to VIN if enable function is not used. Pull it to ground will disable the AOZ1016. Do not leave it open. The voltage on EN pin must be above 2.0V to enable the AOZ1016. When voltage on EN pin falls below 0.6V, the AOZ1016 is disabled. If an application circuit requires the AOZ1016 to be disabled, an open drain or open collector circuit should be used to interface to EN pin.
Switching Frequency
The AOZ1016 switching frequency is fixed and set by an internal oscillator. The actual switching frequency could range from 400kHz to 600kHz due to device variation.
Output Voltage Programming
Output voltage can be set by feeding back the output to the FB pin with a resistor divider network. In the application circuit shown in Figure 1. The resistor divider network includes R2 and R3. Usually, a design is started by picking a fixed R3 value and calculating the required R2 with equation below.
Steady-State Operation
Under steady-state conditions, the converter operates in fixed frequency and Continuous-Conduction Mode (CCM). The AOZ1016 integrates an internal P-MOSFET as the high-side switch. Inductor current is sensed by amplifying the voltage drop across the drain to source of the high side power MOSFET. Output voltage is divided down by the external voltage divider at the FB pin. The difference of the FB pin voltage and reference is amplified by the internal transconductance error amplifier. The error voltage, which shows on the COMP pin, is compared against the current signal, which is sum of inductor current signal and ramp compensation signal, at PWM comparator input. If the current signal is less than the error voltage, the internal high-side switch is on. The inductor current flows from the input through the inductor to the output. When the current signal exceeds the error voltage, the high-side switch is off. The inductor current is freewheeling through the internal Schottky diode to output.
R 2 V O = 0.8 x 1 + ------ R 3
Some standard values of R2, R3 for most commonly used output voltage values are listed in Table 1. Table 1. VO (V)
0.8 1.2 1.5 1.8 2.5 3.3 5.0 1.0 4.99 10 12.7 21.5 31.6 52.3
R2 (k)
10 11.5 10.2 10 10 10
R3 (k)
Open
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AOZ1016
Power-On Reset (POR) The combination of R2 and R3 should be large enough to avoid drawing excessive current from the output, which will cause power loss. Since the switch duty cycle can be as high as 100%, the maximum output voltage can be set as high as the input voltage minus the voltage drop on upper PMOS and inductor. A power-on reset circuit monitors the input voltage. When the input voltage exceeds 4V, the converter starts operation. When input voltage falls below 3.7V, the converter will stop switching. Thermal Protection An internal temperature sensor monitors the junction temperature. It shuts down the internal control circuit and high side PMOS if the junction temperature exceeds 150C.
Protection Features
The AOZ1016 has multiple protection features to prevent system circuit damage under abnormal conditions. Over Current Protection (OCP) The sensed inductor current signal is also used for over current protection. Since the AOZ1016 employs peak current mode control, the COMP pin voltage is proportional to the peak inductor current. The COMP pin voltage is limited to be between 0.4V and 2.5V internally. The peak inductor current is automatically limited cycle by cycle. The cycle by cycle current limit threshold is set between 2.5A and 3.6A. When the load current reaches the current limit threshold, the cycle by cycle current limit circuit turns off the high side switch immediately to terminate the current duty cycle. The inductor current stop rising. The cycle by cycle current limit protection directly limits inductor peak current. The average inductor current is also limited due to the limitation on peak inductor current. When cycle by cycle current limit circuit is triggered, the output voltage drops as the duty cycle decreasing. The AOZ1016 has internal short circuit protection to protect itself from catastrophic failure under output short circuit conditions. The FB pin voltage is proportional to the output voltage. Whenever FB pin voltage is below 0.2V, the short circuit protection circuit is triggered. As a result, the converter is shut down and hiccups at a frequency equal to 1/8 of normal switching frequency. The converter will start up via a soft start once the short circuit condition disappears. In short circuit protection mode, the inductor average current is greatly reduced because of the low hiccup frequency. Output Over Voltage Protection (OVP) The AOZ1016 monitors the feedback voltage: when the feedback voltage is higher than 960mV, it immediately turns-off the PMOS to protect the output voltage overshoot at fault condition. When feedback voltage is lower than 940mV, the PMOS is allowed to turn on in the next cycle.
Application Information
The basic AOZ1016 application circuit is shown in Figure 1. Component selection is explained below. Input Capacitor The input capacitor (C1 in Figure 1) must be connected to the VIN pin and PGND pin of the AOZ1016 to maintain steady input voltage and filter out the pulsing input current. A small decoupling capacitor (Cd in Figure 1), usually 1F, should be connected to the VIN pin and AGND pin for stable operation of the AOZ1016. The voltage rating of input capacitor must be greater than maximum input voltage plus ripple voltage. The input ripple voltage can be approximated by equation below:
IO VO VO V IN = ------------------ x 1 - --------- x --------f x C IN V IN V IN
Since the input current is discontinuous in a buck converter, the current stress on the input capacitor is another concern when selecting the capacitor. For a buck circuit, the RMS value of input capacitor current can be calculated by:
VO VO I CIN _RMS = I O x --------- 1 - --------- V IN V IN
If let m equal the conversion ratio:
VO --------- = m V IN
The relation between the input capacitor RMS current and voltage conversion ratio is calculated and shown in Figure 2. It can be seen that when VO is half of VIN, CIN is under the worst current stress. The worst current stress on CIN is 0.5 x IO.
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AOZ1016
0.5 0.4 ICIN_RMS(m) 0.3 IO 0.2 0.1 0
The inductor takes the highest current in a buck circuit. The conduction loss on inductor needs to be checked for thermal and efficiency requirements. Surface mount inductors in different shape and styles are available from Coilcraft, Elytone and Murata. Shielded inductors are small and radiate less EMI noise. They cost more than unshielded inductors. The choice depends on EMI requirement, price and size. Output Capacitor The output capacitor is selected based on the DC output voltage rating, output ripple voltage specification and ripple current rating. The selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. De-rating needs to be considered for long term reliability. Output ripple voltage specification is another important factor for selecting the output capacitor. In a buck converter circuit, output ripple voltage is determined by inductor value, switching frequency, output capacitor value and ESR. It can be calculated by the equation below:
0
0.5 m
1
Figure 2. ICIN vs. Voltage Conversion Ratio
For reliable operation and best performance, the input capacitors must have current rating higher than ICIN_RMS at worst operating conditions. Ceramic capacitors are preferred for input capacitors because of their low ESR and high ripple current rating. Depending on the application circuits, other low ESR tantalum capacitor or aluminum electrolytic capacitor may also be used. When selecting ceramic capacitors, X5R or X7R type dielectric ceramic capacitors are preferred for their better temperature and voltage characteristics. Note that the ripple current rating from capacitor manufactures is based on certain amount of life time. Further de-rating may be necessary for practical design requirement. Inductor The inductor is used to supply constant current to output when it is driven by a switching voltage. For given input and output voltage, inductance and switching frequency together decide the inductor ripple current, which is:
1 V O = I L x ES R CO + -------------------------- 8xf xC
O where, CO is output capacitor value, and ESRCO is the equivalent series resistance of the output capacitor.
VO VO I L = ----------- x 1 - --------- f xL V IN
The peak inductor current is:
When a low ESR ceramic capacitor is used as an output capacitor, the impedance of the capacitor at the switching frequency dominates. Output ripple is mainly caused by capacitor value and inductor ripple current. The output ripple voltage calculation can be simplified to:
I L I Lpeak = I O + -------2
High inductance gives low inductor ripple current but requires larger size inductor to avoid saturation. Low ripple current reduces inductor core losses. It also reduces RMS current through inductor and switches, which results in less conduction loss. Usually, peak to peak ripple current on inductor is designed to be 20% to 30% of output current. When selecting the inductor, make sure it is able to handle the peak current without saturation even at the highest operating temperature.
1 V O = I L x -------------------------8xf xC
O
If the impedance of ESR at switching frequency dominates, the output ripple voltage is mainly decided by capacitor ESR and inductor ripple current. The output ripple voltage calculation can be further simplified to:
V O = I L x ES R CO
For lower output ripple voltage across the entire operating temperature range, X5R or X7R dielectric type of ceramic, or other low ESR tantalum are recommended to be used as output capacitors.
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AOZ1016
In a buck converter, output capacitor current is continuous. The RMS current of the output capacitor is decided by the peak to peak inductor ripple current. It can be calculated by:
where; GEA is the error amplifier transconductance, which is 200 x 10-6 A/V, GVEA is the error amplifier voltage gain, which is 500 V/V, and CC is compensation capacitor.
I L I CO _RMS = ---------12
Usually, the ripple current rating of the output capacitor is a smaller issue because of the low current stress. When the buck inductor is selected to be very small and inductor ripple current is high, the output capacitor could be overstressed. Loop Compensation The AOZ1016 employs peak current mode control for easy use and fast transient response. Peak current mode control eliminates the double pole effect of the output L&C filter. It greatly simplifies the compensation loop design. With peak current mode control, the buck power stage can be simplified to be a one-pole and one-zero system in frequency domain. The pole is dominant pole and can be calculated by:
The zero given by the external compensation network, capacitor CC (C5 in Figure 1) and resistor RC (R1 in Figure 1), is located at:
1 f Z 2 = -----------------------------------2 x C C x R C
To design the compensation circuit, a target crossover frequency fC for close loop must be selected. The system crossover frequency is where the control loop has unity gain. The crossover frequency is also called the converter bandwidth. Generally, a higher bandwidth means faster response to load transient. However, the bandwidth should not be too high due to system stability concern. When designing the compensation loop, converter stability under all line and load conditions must be considered. Usually, it is recommended to set the bandwidth to be less than 1/10 of the switching frequency. The AOZ1016 operates at a fixed switching frequency range from 350kHz to 600kHz. It is recommended to choose a crossover frequency less than 30kHz.
1 f P 1 = ----------------------------------2 x C O x R L
The zero is a ESR zero due to output capacitor and its ESR. It is can be calculated by:
1 f Z 1 = ------------------------------------------------2 x C O x ESR CO
where; CO is the output filter capacitor, RL is load resistor value, and ESRCO is the equivalent series resistance of output capacitor.
f C = 30kHz
The strategy for choosing RC and CC is to set the cross over frequency with RC and set the compensator zero with CC. Using selected crossover frequency, fC, to calculate RC :
VO 2 x C O R C = f C x ----------- x ----------------------------V G xG
FB EA CS where; fC is the desired crossover frequency, VFB is 0.8V, GEA is the error amplifier transconductance, which is 200 x 10-6 A/V, and GCS is the current sense circuit transconductance, which is 5.64 A/V.
The compensation design is actually to shape the converter close loop transfer function to get the desired gain and phase. Several different types of compensation network can be used for the AOZ1016. In most cases, a series capacitor and resistor network connected to the COMP pin sets the pole-zero and is adequate for a stable high-bandwidth control loop. The FB pin and the COMP pin are the inverting input and the output of internal transconductance error amplifier. A series R and C compensation network connected to COMP provides one pole and one zero. The pole is:
G EA f P 2 = -----------------------------------------2 x C C x G VEA
The compensation capacitor CC and resistor RC together make a zero. This zero is put somewhere close to the dominate pole fp1 but lower than 1/5 of selected crossover frequency. CC can is selected by:
1.5 C C = -----------------------------------2 x R C x f P 1
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Rev. 1.1 September 2007
AOZ1016
The previous equation above can also be simplified to: The maximum junction temperature of AOZ1016 is 150C, which limits the maximum load current capability. Please see the thermal de-rating curves for the maximum load current of the AOZ1016 under different ambient temperatures. The thermal performance of the AOZ1016 is strongly affected by the PCB layout. Extra care should be taken by users during the design process to ensure that the IC will operate under the recommended environmental conditions. Several layout tips are listed below for the best electric and thermal performance. Figure 3 illustrates a single layer PCB layout example as reference. 1. Do not use thermal relief connection to the VIN and the PGND pins. Pour a maximized copper area to the PGND pin and the VIN pin to help thermal dissipation. 2. The input capacitors should be connected as close as possible to the VIN and PGND pins. 3. A ground plane is preferred. If a ground plane is not used, separate PGND from AGND and connect them only at one point to avoid the PGND pin noise coupling to the AGND pin. In this case, a decoupling capacitor should be connected between VIN and AGND. 4. Make the current trace from LX pins to L to CO to the PGND as short as possible. 5. Pour copper plane on all unused board area and connect it to stable DC nodes, like VIN, GND or VOUT. 6. The two LX pins are connected to the internal PFET drain. They are low resistance thermal conduction path and a noisy switching node. Connect a copper plane to the LX pin to help thermal dissipation. This copper plane should not be too large otherwise switching noise may be coupled to other parts of the circuit. 7. Keep sensitive signal traces such as trace connecting FB and COMP away from the LX pins.
CO x RL C C = ---------------------RC
An easy-to-use application software which helps to design and simulate the compensation loop can be found at www.aosmd.com.
Thermal Management and Layout Consideration
In the AOZ1016 buck regulator circuit, high pulsing current flows through two circuit loops. The first loop starts from the input capacitors, to the VIN pin, to the LX pins, to the filter inductor, to the output capacitor and load, and then returns to the input capacitor through ground. Current flows in the first loop when the high side switch is on. The second loop starts from inductor, to the output capacitors and load, to the PGND pin of the AOZ1016, to the LX pins of the AOZ1016. Current flows in the second loop when the low side diode is on. In PCB layout, minimizing the two loops area reduces the noise of this circuit and improves efficiency. A ground plane is recommended to connect input capacitor, output capacitor, and PGND pin of the AOZ1016. In the AOZ1016 buck regulator circuit, the two major power dissipating components are the AOZ1016 and the output inductor. The total power dissipation of converter circuit can be measured by input power minus output power.
P total _loss = V IN x I IN - V O x I O
The power dissipation of inductor can be approximately calculated by output current and DCR of inductor.
P inductor _loss = IO2 x R inductor x 1.1
The actual AOZ1016 junction temperature can be calculated with power dissipation in the AOZ1016 and thermal impedance from junction to ambient.
T junction = ( P total _loss - P inductor _loss ) x + + T ambient
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AOZ1016
Cin
Cd
PGND
VIN AGND
R3
1 2 3 4 SO-8
8 7 6 5
LX LX EN COMP
Cout L
FB
R2 C5 R1
Figure 3. AOZ1016 PCB Layout
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AOZ1016
Package Dimensions, SO-8L
D e 8 L Gauge Plane Seating Plane 0.25
E
E1
h x 45 1 C
7 (4x)
0.1
A2 A
b
A1
Dimensions in millimeters
2.20 Symbols A A1 A2 b c D E1 e E h L Min. 1.35 0.10 1.25 0.31 0.17 4.80 3.80 Nom. 1.65 -- 1.50 -- -- 4.90 3.90 1.27 BSC 5.80 6.00 0.25 -- 0.40 -- 0 -- Max. 1.75 0.25 1.65 0.51 0.25 5.00 4.00 6.20 0.50 1.27 8
Dimensions in inches
Symbols A A1 A2 b c D E1 e E h L Min. 0.053 0.004 0.049 0.012 0.007 0.189 0.150 Nom. Max. 0.065 0.069 -- 0.010 0.059 0.065 -- 0.020 -- 0.010 0.193 0.197 0.154 0.157 0.050 BSC 0.228 0.236 0.244 0.010 -- 0.020 0.016 -- 0.050 0 -- 8
5.74
1.27
0.80 Unit: mm
Notes: 1. All dimensions are in millimeters. 2. Dimensions are inclusive of plating 3. Package body sizes exclude mold flash and gate burrs. Mold flash at the non-lead sides should be less than 6 mils. 4. Dimension L is measured in gauge plane. 5. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact.
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AOZ1016
Tape and Reel Dimensions
SO-8 Carrier Tape
D1 T See Note 5 E1 E2 E P1 P2 See Note 3
See Note 3 B0 K0 A0 Unit: mm Package SO-8 (12mm) A0 6.40 0.10 B0 5.20 0.10 K0 2.10 0.10 D0 1.60 0.10 D1 1.50 0.10 E 12.00 0.10 E1 1.75 0.10 E2 5.50 0.10 P0 8.00 0.10 P1 4.00 0.10 P2 2.00 0.10 T 0.25 0.10 D0 P0 Feeding Direction
SO-8 Reel
W1
S G M V N K
R H W N W Tape Size Reel Size M 12mm o330 o330.00 o97.00 13.00 0.50 0.10 0.30 W1 17.40 1.00 H K o13.00 10.60 +0.50/-0.20 S 2.00 0.50 G -- R -- V --
SO-8 Tape
Leader/Trailer & Orientation
Trailer Tape 300mm min. or 75 empty pockets
Components Tape Orientation in Pocket
Leader Tape 500mm min. or 125 empty pockets
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AOZ1016
AOZ1016 Package Marking
Z1016AL FAYWLT
Part Number Code
Fab & Assembly Location Year & Week Code
Assembly Lot Code
This datasheet contains preliminary data; supplementary data may be published at a later date. Alpha & Omega Semiconductor reserves the right to make changes at any time without notice. LIFE SUPPORT POLICY ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. 2. A critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.
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